Transcript
DATASHEET
S ESIGN EW D N R FO NDED OMME EE EL5364 C E R S NOT
EL5392A
FN7194 Rev 1.00 March 9, 2006
Triple 600MHz Current Feedback Amplifier with Enable The EL5392A is a triple current feedback amplifier with a very high bandwidth of 600MHz. This makes this amplifier ideal for today’s high speed video and monitor applications. With a supply current of just 6mA per amplifier and the ability to run from a single supply voltage from 5V to 10V, the EL5392A is also ideal for hand held, portable or battery powered equipment. The EL5392A also incorporates an enable and disable function to reduce the supply current to 100µA typical per amplifier. Allowing the CE pin to float or applying a low logic level will enable the amplifier. For applications where board space is critical, the EL5392A is offered in the 16 Ld QSOP package, as well as an industry-standard 16 Ld SO (0.150"). The EL5392A operates over the industrial temperature range of -40C to +85C.
Features • 600MHz -3dB bandwidth • 6mA supply current (per amplifier) • Single and dual supply operation, from 5V to 10V • Fast enable/disable • Available in 16 Ld QSOP package • Single (EL5192) and dual (EL5292) available • High speed, 1GHz product available (EL5191) • Low power, 4mA, 300MHz product available (EL5193, EL5293, and EL5393) • Pb-free plus anneal available (RoHS compliant)
Applications • Video amplifiers • Cable drivers
Ordering Information PART NUMBER
PART TAPE & MARKING REEL
PACKAGE
PKG. DWG. #
EL5392ACS
EL5392ACS
-
16 Ld SOIC (0.150")
MDP0027
EL5392ACS-T7
EL5392ACS
7”
16 Ld SOIC (0.150")
MDP0027
EL5392ACS-T13
EL5392ACS
13”
16 Ld SOIC (0.150")
MDP0027
EL5392ACU
5392ACU
-
16 Ld QSOP
MDP0040
EL5392ACU-T13 (Note)
5392ACU
13”
16 Ld QSOP (Pb-free)
MDP0040
EL5392ACUZ (Note)
5392ACUZ
-
16 Ld QSOP (Pb-free)
MDP0040
EL5392ACUZ-T7 (Note)
5392ACUZ
7”
16 Ld QSOP (Pb-free)
MDP0040
16 Ld QSOP (Pb-free)
MDP0040
EL5392ACUZ-T13 5392ACUZ (Note)
13”
• Test equipment • Instrumentation • Current to voltage converters
Pinout EL5392 [16 LD SOIC (0.150") & QSOP] TOP VIEW INA+ 1 CEA 2
16 INA+
VS- 3 CEB 4
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
FN7194 Rev 1.00 March 9, 2006
• RGB amplifiers
14 VS+ + -
INB+ 5
INC+ 8
13 OUTB 12 INB-
NC 6 CEC 7
15 OUTA
11 NC + -
10 OUTC 9 INC-
Page 1 of 14
EL5392A Absolute Maximum Ratings (TA = 25°C) Supply Voltage Between VS+ and VS-. . . . . . . . . . . . . . . . . . . . . 11V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . 125°C Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . .VS- - 0.5V to VS+ +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications PARAMETER
VS+ = +5V, VS- = -5V, RF = 750 for AV = 1, RF = 375 for AV = 2, RL = 150, TA = 25°C unless otherwise specified. DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE BW
-3dB Bandwidth
AV = +1
600
MHz
AV = +2
300
MHz
25
MHz
2300
V/µs
BW1
0.1dB Bandwidth
SR
Slew Rate
VO = -2.5V to +2.5V, AV = +2
tS
0.1% Settling Time
VOUT = -2.5V to +2.5V, AV = -1
9
ns
CS
Channel Separation
f = 5MHz
60
dB
eN
Input Voltage Noise
4.1
nV/Hz
iN-
IN- Input Current Noise
20
pA/Hz
iN+
IN+ Input Current Noise
50
pA/Hz
dG
Differential Gain Error (Note 1)
AV = +2
0.015
%
dP
Differential Phase Error (Note 1)
AV = +2
0.04
°
2000
DC PERFORMANCE VOS
Offset Voltage
TCVOS
Input Offset Voltage Temperature Coefficient Measured from TMIN to TMAX
ROL
Transimpediance
-10
1
10
mV
5
µV/°C
200
400
k
INPUT CHARACTERISTICS CMIR
Common Mode Input Range
±3
±3.3
V
CMRR
Common Mode Rejection Ratio
42
50
dB
+IIN
+ Input Current
-60
3
60
µA
-IIN
- Input Current
-40
4
40
µA
RIN
Input Resistance
37
k
CIN
Input Capacitance
0.5
pF
OUTPUT CHARACTERISTICS VO
RL = 150 to GND
±3.4
±3.7
V
RL = 1k to GND
±3.8
±4.0
V
Output Current
RL = 10 to GND
95
120
mA
ISON
Supply Current - Enabled
No load, VIN = 0V
5
6
7.5
mA
ISOFF
Supply Current - Disabled
No load, VIN = 0V
100
150
µA
IOUT
Output Voltage Swing
SUPPLY
FN7194 Rev 1.00 March 9, 2006
Page 2 of 14
EL5392A Electrical Specifications PARAMETER
VS+ = +5V, VS- = -5V, RF = 750 for AV = 1, RF = 375 for AV = 2, RL = 150, TA = 25°C unless otherwise specified. (Continued) DESCRIPTION
CONDITIONS
MIN
TYP 75
PSRR
Power Supply Rejection Ratio
DC, VS = ±4.75V to ±5.25V
55
-IPSR
- Input Current Power Supply Rejection
DC, VS = ±4.75V to ±5.25V
-2
MAX
UNIT dB
2
µA/V
ENABLE tEN
Enable Time
40
ns
tDIS
Disable Time
600
ns
IIHCE
CE Pin Input High Current
CE = VS+
0.8
6
µA
IILCE
CE Pin Input Low Current
CE = VS-
0
-0.1
µA
VIHCE
CE Input High Voltage for Power-down
VILCE
CE Input Low Voltage for Power-down
VS+ - 1
V VS+ - 3
V
NOTE: 1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.58MHz
FN7194 Rev 1.00 March 9, 2006
Page 3 of 14
EL5392A
Typical Performance Curves Non-Inverting Frequency Response (Gain)
Non-Inverting Frequency Response (Phase)
6
90 AV=2
2
0
-2
-90
AV=1 AV=2
Phase (°)
Normalized Magnitude (dB)
AV=1
AV=5 -6
AV=5 AV=10
-180
AV=10 -10
-270
-14 1M
RF=750 RL=150 10M
100M
-360 1M
1G
RF=750 RL=150 10M
Frequency (Hz)
Inverting Frequency Response (Gain) 90 AV=-1
2
AV=-2
AV=-1
0
Phase (°)
-2 AV=-5 -6
-10
-90
AV=-2 AV=-5
-180
-270
-14 1M
RF=375 RL=150 10M
100M
-360 1M
1G
RF=375 RL=150 10M
Frequency (Hz)
100M
Frequency Response for Various RL
10
6 RL=150 Normalized Magnitude (dB)
Normalized Magnitude (dB)
2pF added 6 1pF added 2
-2
-6
-10 1M
1G
Frequency (Hz)
Frequency Response for Various CIN-
0pF added
AV=2 RF=375 RL=150 10M
100M
Frequency (Hz)
FN7194 Rev 1.00 March 9, 2006
1G
Inverting Frequency Response (Phase)
6
Normalized Magnitude (dB)
100M Frequency (Hz)
1G
RL=100
2 RL=500
-2
-6
-10
-14 1M
AV=2 RF=375 10M
100M
1G
Frequency (Hz)
Page 4 of 14
EL5392A
Typical Performance Curves
(Continued)
Frequency Response for Various CL
Frequency Response for Various RF 6
AV=2 RF=375 RL=150
10
250 Normalized Magnitude (dB)
Normalized Magnitude (dB)
14
12pF added
6
8pF added
2
0pF added
-2
-6 1M
10M
100M
475 -2
620
-6
750
-10
-14 1M
1G
AV=2 RG=RF RL=150 10M
Frequency (Hz)
100M
1G
Frequency (Hz) Frequency Response for Various Common-Mode Input Voltages
Group Delay vs Frequency 3.5
6 VCM=3V
2.5
Normalized Magnitude (dB)
3 Group Delay (ns)
375
2
AV=2 RF=375
2 1.5 1
AV=1 RF=750
0.5 0 1M
100M
10M
-2
VCM=-3V
-6
-10
-14 1M
1G
VCM=0V
2
AV=2 RF=375 RL=150 10M
100M
1G
Frequency (Hz)
Frequency (Hz) Transimpedance (ROL) vs Frequency
PSRR and CMRR vs Frequency 20
10M 0 Phase
100k -180 10k -270
Gain 1k
PSRR/CMRR (dB)
0 -90 Phase (°)
Magnitude ()
1M
PSRR+
-20 PSRR-40
-60
CMRR
-360 100 1k
10k
100k
1M
10M
Frequency (Hz)
FN7194 Rev 1.00 March 9, 2006
100M
1G
-80 10k
100k
1M
10M
100M
1G
Frequency (Hz)
Page 5 of 14
EL5392A
Typical Performance Curves
(Continued)
-3dB Bandwidth vs Supply Voltage for Non-Inverting Gains
-3dB Bandwidth vs Supply Voltage for Inverting Gains
800
350 300
600
AV=1
-3dB Bandwidth (MHz)
-3dB Bandwidth (MHz)
RF=750 RL=150
400
AV=2
200
AV=5
AV=10
AV=-1
250 AV=-2 200 AV=-5 150 100 50
0
RF=375 RL=150
0 5
6
7
8
9
5
10
6
7
Total Supply Voltage (V)
Peaking vs Supply Voltage for Non-Inverting Gains
10
4 RF=750 RL=150
3
3
AV=1
2
1
RF=375 RL=150
AV=-1
Peaking (dB)
Peaking (dB)
9
Peaking vs Supply Voltage for Inverting Gains
4
AV=-2
2
1
AV=2
AV=10
AV=-5
0
0 5
6
7
8
9
5
10
6
7
Total Supply Voltage (V)
AV=1
-3dB Bandwidth (MHz)
400
800 600 400
0 -40
AV=2
10
AV=5
60
AV=10
110
Ambient Temperature (°C)
FN7194 Rev 1.00 March 9, 2006
10
500 RF=750 RL=150
1000
200
9
-3dB Bandwidth vs Temperature for Inverting Gains
1400 1200
8
Total Supply Voltage (V)
-3dB Bandwidth vs Temperature for Non-Inverting Gains
-3dB Bandwidth (MHz)
8
Total Supply Voltage (V)
160
300
RF=375 RL=150
AV=-1
AV=-2
200 AV=-5 100
0 -40
10
60
110
160
Ambient Temperature (°C)
Page 6 of 14
EL5392A
Typical Performance Curves
(Continued)
Peaking vs Temperature
Voltage and Current Noise vs Frequency
2
1k RL=150 AV=1
Voltage Noise (nV/Hz) Current Noise (pA/Hz)
Peaking (dB)
1.5
1 AV=-1 0.5
AV=-2
0
i n+
100 i n10
en
AV=2
-0.5 -50
-50
0
50
1 100
100
1k
10k
100
10
10
8 Supply Current (mA)
Output Impedance ()
1M
10M
Supply Current vs Supply Voltage
Closed Loop Output Impedance vs Frequency
1
0.1
0.01
0.001
6
4
2
0
100
1k
10k
1M
100k
10M
100M
1G
0
2
4
6
8
10
12
Supply Voltage (V)
Frequency (Hz)
2nd and 3rd Harmonic Distortion vs Frequency
Two-Tone 3rd Order Input Referred Intermodulation Intercept (IIP3)
-20
30 AV=+2 VOUT=2VP-P RL=100
-40 -50
2nd Order Distortion
-60 -70
3rd Order Distortion
-80 -90
20 15 10 5 0 -5 -10
-100 1
10 Frequency (MHz)
FN7194 Rev 1.00 March 9, 2006
AV=+2 RL=150
25 Input Power Intercept (dBm)
-30 Harmonic Distortion (dBc)
100k
Frequency (Hz)
Ambient Temperature (°C)
100
-15 10
AV=+2 RL=100 100
200
Frequency (MHz)
Page 7 of 14
EL5392A
Typical Performance Curves
(Continued)
Differential Gain/Phase vs DC Input Voltage at 3.58MHz
Differential Gain/Phase vs DC Input Voltage at 3.58MHz
0.03
0.03 AV=2 RF=RG=375 RL=150
dG (%) or dP (°)
0.01
AV=1 RF=750 RL=500
0.02 dP
0.01 dG (%) or dP (°)
0.02
0 dG
-0.01 -0.02 -0.03
dP
0
dG
-0.01 -0.02 -0.03 -0.04
-0.04
-0.05
-0.05 -1
-0.5
0
0.5
-0.06 -1
1
-0.5
DC Input Voltage Output Voltage Swing vs Frequency THD<1%
1
10
7
RL=500 Output Voltage Swing (VPP)
RL=500
8 RL=150
6 5 4 3 2 1
AV=2
0 1
8
RL=150
6
4
2 AV=2
0 10
100
1
Frequency (MHz)
10
Large Signal Step Response VS=±5V RL=150 AV=2 RF=RG=375
200mV/div
100
Frequency (MHz)
Small Signal Step Response
VS=±5V RL=150 AV=2 RF=RG=375
1V/div
10ns/div
FN7194 Rev 1.00 March 9, 2006
0.5
Output Voltage Swing vs Frequency THD<0.1%
9
Output Voltage Swing (VPP)
0 DC Input Voltage
10ns/div
Page 8 of 14
EL5392A
Typical Performance Curves
(Continued)
Settling Time vs Settling Accuracy
Transimpedance (RoI) vs Temperature
25
500 AV=2 RF=RG=375 RL=150 VSTEP=5VP-P output
450
15
RoI (k)
Settling Time (ns)
20
10
400
350
5
0 0.01
0.1
300 -40
1
10
Settling Accuracy (%)
PSRR and CMRR vs Temperature
PSRR
2 ICMR/IPSR (µA/V)
70 PSRR/CMRR (dB)
160
110
160
2.5
80
60 CMRR 50 40 30
ICMR+
1.5 1 IPSR
0.5 0
ICMR-
-0.5
20 10 -40
10
60
110
-1 -40
160
10
Die Temperature (°C)
Input Current vs Temperature
3
60 40 Input Current (µA)
2
1
0
-1
-2 -40
60 Die Temperature (°C)
Offset Voltage vs Temperature
VOS (mV)
110
ICMR and IPSR vs Temperature
90
20 IB0 -20 IB+
-40 -60
10
60 Die Temperature (°C)
FN7194 Rev 1.00 March 9, 2006
60 Die Temperature (°C)
110
160
-80 -40
10
60
110
160
Temperature (°C)
Page 9 of 14
EL5392A
Typical Performance Curves
(Continued)
Positive Input Resistance vs Temperature
Supply Current vs Temperature
50
8
45
7 Supply Current (mA)
40
RIN+ (k)
35 30 25 20 15 10
6 5 4 3 2 1
5 0 -40
10
60
110
0 -40
160
10
Temperature (°C)
Positive Output Swing vs Temperature for Various Loads -3.5
4.1
-3.6 1k
VOUT (V)
VOUT (V)
3.8
150
-3.8 -3.9 1k
-4
150
-4.1
3.6 3.5 -40
10
50
110
-4.2 -40
160
10
Output Current vs Temperature
160
Slew Rate vs Temperature
135
4600 AV=2 RF=RG=375 RL=150
4400 4200
Sink
Slew Rate (V/µS)
130
110
60 Temperature (°C)
Temperature (°C)
IOUT (mA)
160
-3.7
3.9
3.7
110
Negative Output Swing vs Temperature for Various Loads
4.2
4
60 Temperature (°C)
125 Source 120
4000 3800 3600 3400 3200
115 -40
10
60 Die Temperature (°C)
FN7194 Rev 1.00 March 9, 2006
110
160
3000 -40
10
60
110
160
Die Temperature (°C)
Page 10 of 14
EL5392A
Typical Performance Curves
(Continued) Package Power Dissipation vs Ambient Temperature JEDEC JESD51-3 Low Effective Thermal Conductivity Test Board
Channel-to-Channel Isolation vs Frequency 0
1 0.9 0.8 Power Dissipation (W)
Gain (dB)
-20
-40
-60
-80
909mW
0.7 0.6
633mW
0.5 0.4 0.3
SO 16 (0 11 .1 0° 50 C ”) /W QS OP 15 16 8° C/ W
0.2 0.1
-100 100k
0 1M
10M
100M
400M
0
Frequency (Hz)
25
50
75 85
100
125
150
Ambient Temperature (°C)
Enable Response
Disable Response
500mV/div
500mV/div
5V/div 5V/div
20ns/div
FN7194 Rev 1.00 March 9, 2006
400ns/div
Page 11 of 14
EL5392A
Pin Descriptions 16 Ld SOIC (0.150")
16 Ld QSOP
Pin Name
1
1
INA+
Function
Equivalent Circuit
Non-inverting input, channel A
VS+
IN+
IN-
VSCircuit 1
2
2
CEA
Chip enable, channel A
VS+
CE
VSCircuit 2
3
3
VS-
Negative supply
4
4
CEB
Chip enable, channel B
(See circuit 2)
5
5
INB+
Non-inverting input, channel B
(See circuit 1)
6, 11
6, 11
NC
7
7
CEC
Chip enable, channel C
(See circuit 2)
8
8
INC+
Non-inverting input, channel C
(See circuit 1)
9
9
INC-
Inverting input, channel C
(See circuit 1)
10
10
OUTC
Not connected
Output, channel C
VS+
OUT
VSCircuit 3
12
12
INB-
13
13
OUTB
14
14
VS+
15
15
OUTA
16
16
INA-
Inverting input, channel B
(See circuit 1)
Output, channel B
(See circuit 3)
Positive supply Output, channel A
(See circuit 3)
Inverting input, channel A
(See circuit 1)
Applications Information Product Description The EL5392A is a current-feedback operational amplifier that offers a wide -3dB bandwidth of 600MHz and a low supply current of 6mA per amplifier. The EL5392A works with supply voltages ranging from a single 5V to 10V and they are also capable of swinging to within 1V of either supply on the output. Because of their current-feedback topology, the EL5392A does not have the normal gainbandwidth product associated with voltage-feedback operational amplifiers. Instead, its -3dB bandwidth to remain
FN7194 Rev 1.00 March 9, 2006
relatively constant as closed-loop gain is increased. This combination of high bandwidth and low power, together with aggressive pricing make the EL5392A the ideal choice for many low-power/high-bandwidth applications such as portable, handheld, or battery-powered equipment. For varying bandwidth needs, consider the EL5191 with 1GHz on a 9mA supply current or the EL5193 with 300MHz on a 4mA supply current. Versions include single, dual, and triple amp packages with 5 Ld SOT-23, 16 Ld QSOP, and 8 Ld or 16 Ld SOIC (0.150") outlines.
Page 12 of 14
EL5392A Power Supply Bypassing and Printed Circuit Board Layout As with any high frequency device, good printed circuit board layout is necessary for optimum performance. Low impedance ground plane construction is essential. Surface mount components are recommended, but if leaded components are used, lead lengths should be as short as possible. The power supply pins must be well bypassed to reduce the risk of oscillation. The combination of a 4.7µF tantalum capacitor in parallel with a 0.01µF capacitor has been shown to work well when placed at each supply pin. For good AC performance, parasitic capacitance should be kept to a minimum, especially at the inverting input. (See the Capacitance at the Inverting Input section) Even when ground plane construction is used, it should be removed from the area near the inverting input to minimize any stray capacitance at that node. Carbon or Metal-Film resistors are acceptable with the Metal-Film resistors giving slightly less peaking and bandwidth because of additional series inductance. Use of sockets, particularly for the SOIC (0.150") package, should be avoided if possible. Sockets add parasitic inductance and capacitance which will result in additional peaking and overshoot.
Disable/Power-Down The EL5392A amplifier can be disabled placing its output in a high impedance state. When disabled, the amplifier supply current is reduced to < 450µA. The EL5392A is disabled when its CE pin is pulled up to within 1V of the positive supply. Similarly, the amplifier is enabled by floating or pulling its CE pin to at least 3V below the positive supply. For ±5V supply, this means that an EL5392A amplifier will be enabled when CE is 2V or less, and disabled when CE is above 4V. Although the logic levels are not standard TTL, this choice of logic voltages allows the EL5392A to be enabled by tying CE to ground, even in 5V single supply applications. The CE pin can be driven from CMOS outputs.
Capacitance at the Inverting Input Any manufacturer’s high-speed voltage- or current-feedback amplifier can be affected by stray capacitance at the inverting input. For inverting gains, this parasitic capacitance has little effect because the inverting input is a virtual ground, but for non-inverting gains, this capacitance (in conjunction with the feedback and gain resistors) creates a pole in the feedback path of the amplifier. This pole, if low enough in frequency, has the same destabilizing effect as a zero in the forward open-loop response. The use of largevalue feedback and gain resistors exacerbates the problem by further lowering the pole frequency (increasing the possibility of oscillation.) The EL5392A has been optimized with a 375 feedback resistor. With the high bandwidth of these amplifiers, these resistor values might cause stability problems when combined with parasitic capacitance, thus ground plane is
FN7194 Rev 1.00 March 9, 2006
not recommended around the inverting input pin of the amplifier.
Feedback Resistor Values The EL5392A has been designed and specified at a gain of +2 with RF approximately 375. This value of feedback resistor gives 300MHz of -3dB bandwidth at AV=2 with 2dB of peaking. With AV=-2, an RF of 375 gives 275MHz of bandwidth with 1dB of peaking. Since the EL5392A is a current-feedback amplifier, it is also possible to change the value of RF to get more bandwidth. As seen in the curve of Frequency Response for Various RF and RG, bandwidth and peaking can be easily modified by varying the value of the feedback resistor. Because the EL5392A is a current-feedback amplifier, its gain-bandwidth product is not a constant for different closedloop gains. This feature actually allows the EL5392A to maintain about the same -3dB bandwidth. As gain is increased, bandwidth decreases slightly while stability increases. Since the loop stability is improving with higher closed-loop gains, it becomes possible to reduce the value of RF below the specified 375 and still retain stability, resulting in only a slight loss of bandwidth with increased closed-loop gain.
Supply Voltage Range and Single-Supply Operation The EL5392A has been designed to operate with supply voltages having a span of greater than 5V and less than 10V. In practical terms, this means that the EL5392A will operate on dual supplies ranging from ±2.5V to ±5V. With singlesupply, the EL5392A will operate from 5V to 10V. As supply voltages continue to decrease, it becomes necessary to provide input and output voltage ranges that can get as close as possible to the supply voltages. The EL5392A has an input range which extends to within 2V of either supply. So, for example, on ±5V supplies, the EL5392A has an input range which spans ±3V. The output range of the EL5392A is also quite large, extending to within 1V of the supply rail. On a ±5V supply, the output is therefore capable of swinging from -4V to +4V. Single-supply output range is larger because of the increased negative swing due to the external pull-down resistor to ground.
Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150, because of the change in output current with DC level. Previously, good differential gain could only be achieved by running high idle currents through the output transistors (to reduce variations in output impedance.) These currents were typically comparable to the entire 6mA supply current of each EL5392A amplifier. Special circuitry has been incorporated in the EL5392A to reduce the
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EL5392A variation of output impedance with current output. This results in dG and dP specifications of 0.015% and 0.04°, while driving 150 at a gain of 2. Video performance has also been measured with a 500 load at a gain of +1. Under these conditions, the EL5392A has dG and dP specifications of 0.03% and 0.05°, respectively.
Output Drive Capability In spite of its low 6mA of supply current, the EL5392A is capable of providing a minimum of ±95mA of output current. With a minimum of ±95mA of output drive, the EL5392A is capable of driving 50 loads to both rails, making it an excellent choice for driving isolation transformers in telecommunications applications.
Driving Cables and Capacitive Loads When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5392A from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. In these applications, a small series resistor (usually between 5 and 50) can be placed in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. In many cases it is also possible to simply increase the value of the feedback resistor (RF) to reduce the peaking.
Power Dissipation With the high output drive capability of the EL5392A, it is possible to exceed the 125°C Absolute Maximum junction temperature under certain very high load current conditions. Generally speaking when RL falls below about 25, it is important to calculate the maximum junction temperature (TJMAX) for the application to determine if power supply voltages, load conditions, or package type need to be modified for the EL5392A to remain in the safe operating area. These parameters are calculated as follows: T JMAX = T MAX + JA n PD MAX
where: TMAX = Maximum ambient temperature JA = Thermal resistance of the package n = Number of amplifiers in the package PDMAX = Maximum power dissipation of each amplifier in the package PDMAX for each amplifier can be calculated as follows: V OUTMAX PDMAX = 2 V S I SMAX + V S - V OUTMAX ---------------------------R L
where: VS = Supply voltage
Current Limiting
ISMAX = Maximum supply current of 1A
The EL5392A has no internal current-limiting circuitry. If the output is shorted, it is possible to exceed the Absolute Maximum Rating for output current or power dissipation, potentially resulting in the destruction of the device.
VOUTMAX = Maximum output voltage (required) RL = Load resistance
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For additional products, see www.intersil.com/en/products.html Intersil products are manufactured, assembled and tested utilizing ISO9001 quality systems as noted in the quality certifications found at www.intersil.com/en/support/qualandreliability.html Intersil products are sold by description only. Intersil may modify the circuit design and/or specifications of products at any time without notice, provided that such modification does not, in Intersil's sole judgment, affect the form, fit or function of the product. Accordingly, the reader is cautioned to verify that datasheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com
FN7194 Rev 1.00 March 9, 2006
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